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ADP3801AR

更新时间： 2024-01-21 17:58:34
品牌 Logo 应用领域
亚德诺 - ADI 电池开关
页数 文件大小 规格书
20页 258K
描述
High Frequency Switch Mode Dual Li-Ion Battery Chargers

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中文翻译

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ADP3801AR 技术参数

是否无铅： 含铅是否Rohs认证： 不符合
生命周期：Active零件包装代码：SOIC
包装说明：SOP,针数：16
Reach Compliance Code：unknown风险等级：5.72
模拟集成电路 - 其他类型：BATTERY CHARGE CONTROLLER控制模式：CURRENT/VOLTAGE-MODE
控制技术：PULSE WIDTH MODULATION最大输入电压：20 V
最小输入电压：4.1 V标称输入电压：10 V
JESD-30 代码：R-PDSO-G16JESD-609代码：e0
长度：9.9 mm湿度敏感等级：NOT SPECIFIED
功能数量：1端子数量：16
最高工作温度：85 °C最低工作温度：-40 °C
标称输出电压：3.3 V封装主体材料：PLASTIC/EPOXY
封装代码：SOP封装形状：RECTANGULAR
封装形式：SMALL OUTLINE峰值回流温度（摄氏度）：220
认证状态：COMMERCIAL座面最大高度：1.75 mm
表面贴装：YES切换器配置：SINGLE
最大切换频率：250 kHz温度等级：INDUSTRIAL
端子面层：TIN LEAD端子形式：GULL WING
端子节距：1.27 mm端子位置：DUAL
处于峰值回流温度下的最长时间：30宽度：3.9 mm
Base Number Matches：1

ADP3801AR 数据手册

 浏览型号ADP3801AR的Datasheet PDF文件第11页浏览型号ADP3801AR的Datasheet PDF文件第12页浏览型号ADP3801AR的Datasheet PDF文件第13页浏览型号ADP3801AR的Datasheet PDF文件第15页浏览型号ADP3801AR的Datasheet PDF文件第16页浏览型号ADP3801AR的Datasheet PDF文件第17页 
ADP3801/ADP3802  
Gate Drive  
to CIN, a 0.1 µF decoupling capacitor is required as close as  
The ADP3801 and ADP3802 are designed to directly drive the  
gate of a PFET with no additional circuitry as shown on the  
circuit diagram. The DRV pin pulls the gate up to within  
250 mV of VCC, which is more than enough to ensure that the  
transistor turns off. To turn the PFET on, the DRV pin pulls  
down to a clamped voltage that is at most 7 V below VCC. Check  
the specified PFET’s maximum Gate-Source rating to see if this  
voltage does not exceed its breakdown. The Si4463 is rated at  
VGSMAX = 12 V, which is well above the maximum gate drive for  
the ADP3801/ADP3802.  
possible to the VCC pin.  
Once the capacitor is chosen, the input ripple voltage should be  
checked:  
D
ON /100  
84/100  
V
= IO  
×
ESR +  
= 4.0 A × 0.07 Ω +  
= 360 mVPP  
INRIPPLE  
fOSC × CIN  
200 kHz × 210 µF  
This is low enough for most applications. For cost reduction,  
one of the 68 µF capacitors could be removed, or a cheaper  
electrolytic could be used instead.  
Output Capacitor Selection  
Schottky Rectifier Selection and Thermal Design  
The Schottky diode’s peak current and average power dissipa-  
tion must not exceed the diode ratings. The most stressful con-  
dition for the output diode is under short circuit (VO = 0 V),  
where the diode duty cycle DD is at least 95%. Under this con-  
dition, the diode must safely handle IPK at close to 100% duty  
cycle.  
As a first choice, we’ll use two of the same type of 68 µF  
Sprague capacitors for the output. The inductor rms ripple current  
was calculated as 0.3 A, which is far below the specification for  
these capacitors. The other consideration is the allowable output  
ripple voltage. Assuming high battery internal resistance, all of  
the worst case inductor ripple current may flow through the  
output capacitor. This results in a ripple voltage of:  
The diode power dissipation (PD) is calculated by multiplying  
the forward voltage drop (VF) times the Schottky diode duty  
cycle multiplied by the short circuit current. The worst-case  
D
ON /100  
84/100  
VOUTRIPPLE = ILPP  
×
ESR +  
= 1.0 A × 0.1Ω +  
= 130 mVPP  
fOSC × COUT  
200 kHz ×140 µF  
forward voltage drop of MBRD835 diode is 0.41 V at IPK  
4.5 A, thus:  
=
This ripple is low enough for most applications. Again, one of  
the capacitors could be removed or lower cost electrolytic ca-  
pacitors could be used to reduce cost.  
P
D = IPK × DD × VF = 4.5 × 0.95 × 0.41 = 1.8W  
From the diode’s worst-case dissipation, the maximum junction  
temperature TJMAX of the diode can be calculated:  
Charger Performance Summary  
The circuit properly executes the charging algorithm, exhibiting  
stable operation regardless of battery conditions, including an  
open circuit load in which the battery is removed.  
TJMAX = TA + RθJA × PD = 25 + (40) × 1.8 = 97°C  
R
θJA is the junction to ambient thermal impedance of the diode.  
Li-Ion charging characteristics are given in Figure 25. The  
charge current is maintained at its programmed level until the  
battery reaches its final voltage. Then the current begins to  
decrease. The shape of the current decrease is dependent on the  
internal impedance of the battery. When the current drops below  
240 mA, the EOC comparator signals the end-of-charge of the  
battery.  
The calculated TJMAX should be below the maximum allowed  
junction temperature of the diode with adequate margin. TJMAX  
of the MBRD835 is 125°C, which is met with adequate margin.  
Input Capacitor Selection  
In continuous mode, the source current of the PMOS is a square  
wave of duty cycle VOUT/VIN. To prevent large voltage tran-  
sients, a low ESR input capacitor sized for the maximum rms  
current must be used. The maximum rms capacitor current is  
given by:  
4.5  
4.0  
V
BAT  
IOUT  
3.5  
3.0  
2.5  
IRMS  
≈
× VOUT V −VOUT  
IN  
(
)
V
IN  
This formula has a maximum at VIN = 2 VOUT, where IRMS  
OUT/2 = 2.0 A.  
=
I
I
This simple worst case condition is commonly used for design  
because even significant deviations do not offer much relief.  
Note that capacitor manufacturers’ ripple current ratings are  
often based on only 2000 hours of life. This makes it advisable  
to further derate the capacitor, or to choose a capacitor rated at  
a higher temperature than required. Several capacitors may also  
be paralleled to meet size or height requirements in the design.  
As a first choice, three 68 µF/20 V Sprague type 593D tantalum  
capacitors are used in parallel. Each is specified as follows:  
ESR = 0.2 Ω, maximum ripple current of 0.91ARMS. In addition  
CHARGE  
4.0  
2.7  
1.3  
EOC  
0
0
0.5  
1.0  
1.5  
2.0  
2.5  
3.0  
TIME – Hours  
Figure 25. Li-Ion Charging Characteristic  
–14–  
REV. 0  
1...11121314151617...20

中文翻译

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