AD626
+INPUT
–INPUT
The output of A1 is connected to the input of A2 via a 100 kΩ
(R12) resistor to facilitate the low-pass filtering of the signal of
interest (see Low-Pass Filtering section).
200k⍀
200k⍀
+IN
–IN
1
2
3
8
7
6
5
The 200 kΩ input impedance of the AD626 requires that the
source resistance driving this amplifier be low in value (<1 kΩ)—
this is necessary to minimize gain error. Also, any mismatch
between the total source resistance at each input will affect gain
accuracy and common-mode rejection (CMR). For example:
when operating at a gain of 10, an 80 Ω mismatch in the source
resistance between the inputs will degrade CMR to 68 dB.
1/6
ANALOG
GND
NOT
CONNECTED
G = 100
G=30
–V
+V
S
–V
S
+V
S
S
0.1F
100k⍀
FILTER
0.1F
OUT
=
OUTPUT
G
2
4
The output buffer, A2, operates at a gain of 2 or 20, thus setting
the overall, precalibrated gain of the AD626 (with no external
components) at 10 or 100. The gain is set by the feedback net-
work around amplifier A2.
AD626
Figure 29. AD626 Configured for a Gain of 10
+INPUT
The output of amplifier A2 relies on a 10 kΩ resistor to –VS for
“pulldown.” For single supply operation, (–VS = “GND”), A2
can drive a 10 kΩ ground referenced load to at least +4.7 V.
The minimum, nominally “zero,” output voltage will be 30 mV.
For dual supply operation (±5 V), the positive output voltage
swing will be the same as for a single supply. The negative swing
will be to –2.5 V, at G = 100, limited by the ratio:
200k⍀
200k⍀
+IN
–IN
–INPUT
1
2
3
8
7
6
5
1/6
ANALOG
GND
G = 100
G=30
–V
+V
–V
S
+V
S
S
R15 + R14
–VS ×
S
0.1F
100k⍀
FILTER
0.1F
OUTPUT
R13 + R14 + R15
OUT
=
G
2
4
The negative range can be extended to –3.3 V (G = 100) and
–4 V (G = 10) by adding an external 10 kΩ pulldown from the
output to –VS. This will add 0.5 mA to the AD626’s quiescent
current, bringing the total to 2 mA.
AD626
Figure 30. AD626 Configured for a Gain of 100
The AD626’s 100 kHz bandwidth at G = 10 and 100 (a 10 MHz
gain bandwidth) is much higher than can be obtained with low
power op amps in discrete differential amplifier circuits. Fur-
thermore, the AD626 is stable driving capacitive loads up to
50 pF (G10) or 200 pF (G100). Capacitive load drive can be
increased to 200 pF (G10) by connecting a 100 Ω resistor in
series with the AD626’s output and the load.
+INPUT
200k⍀
200k⍀
+IN
–IN
–INPUT
8
7
6
5
1
2
3
1/6
R
H
ANALOG
GND
G = 100
R
G
G=30
–V
+V
–V
S
+V
S
S
S
ADJUSTING THE GAIN OF THE AD626
100k⍀
FILTER
0.1F
0.1F
The AD626 is easily configured for gains of 10 or 100. Figure
29 shows that for a gain of 10, Pin 7 is simply left unconnected;
similarly, for a gain of 100, Pin 7 is grounded, as shown in Fig-
ure 30.
OUT
=
G
OUTPUT
2
4
CF
FILTER
(OPTIONAL)
AD626
1
CORNER FREQUENCY OF FILTER =
Gains between 10 and 100 are easily set by connecting a vari-
able resistance between Pin 7 and Analog GND, as shown in
Figure 31. Because the on-chip resistors have an absolute toler-
ance of ±20% (although they are ratio matched to within 0.1%),
at least a 20% adjustment range must be provided. The values
shown in the table in Figure 31 provide a good trade-off be-
tween gain set range and resolution, for gains from 11 to 90.
2CF (100k⍀)
RESISTOR VALUES FOR GAIN ADJUSTMENT
GAIN RANGE
R
(⍀)
R (⍀)
H
G
4.99k
802
80
11 – 20
20 – 40
40 – 80
80 – 100
100k
10k
1k
2
100
Figure 31. Recommended Circuit for Gain Adjustment
–10–
REV. C